Colpitts oscillator

A Colpitts oscillator, invented in 1918 and patented 1927^[1] by American engineer Edwin H. Colpitts, is one of a number of designs for LC oscillators, electronic oscillators that use a combination of inductors (L) and capacitors (C) to determine the frequency of oscillation. The distinguishing feature of the Colpitts oscillator is that the feedback for the active device is taken from a voltage divider made of two capacitors in series across the inductor.^[2]^[3]^[4]^[5]

1 Overview
- 1.1 Practical example
2 Theory
- 2.1 Oscillation amplitude
3 External links
4 References

Overview [edit]

Figure 1: Simple common base Colpitts oscillator (with simplified biasing)	Figure 2: Simple common collector Colpitts oscillator (with simplified biasing)
Figure 3: Practical common base Colpitts oscillator (with an oscillation frequency of ~50 MHz)

The Colpitts circuit, like other LC oscillators, consists of a gain device, such as a transistor or vacuum tube, with its output connected to its input in a feedback loop containing a parallel LC circuit (tuned circuit) which functions as a bandpass filter to set the frequency of oscillation.

A Colpitts oscillator is the electrical dual of a Hartley oscillator, where the feedback signal is taken from an "inductive" voltage divider consisting of two coils in series (or a tapped coil). Fig. 1 shows the common-base Colpitts circuit. L and the series combination of C₁ and C₂ form the parallel resonant tank circuit which determines the frequency of the oscillator. The voltage across C₂ is applied to the base-emitter junction of the transistor, as feedback to create oscillations. Fig. 2 shows the common-collector version. Here the voltage across C₁ provides feedback. The frequency of oscillation is approximately the resonant frequency of the LC circuit, which is the series combination of the two capacitors in parallel with the inductor

$f_0 = {1 \over 2 \pi \sqrt {L \left ({ C_1 C_2 \over C_1 + C_2 }\right ) }}$

The actual frequency of oscillation will be slightly lower due to junction capacitances and resistive loading of the transistor.

As with any oscillator, the amplification of the active component should be marginally larger than the attenuation of the capacitive voltage divider, to obtain stable operation. Thus, a Colpitts oscillator used as a variable frequency oscillator (VFO) performs best when a variable inductance is used for tuning, as opposed to tuning one of the two capacitors. If tuning by variable capacitor is needed, it should be done via a third capacitor connected in parallel to the inductor (or in series as in the Clapp oscillator).

Practical example [edit]

Fig. 3 shows a working example with component values. Instead of bipolar junction transistors, other active components such as field effect transistors or vacuum tubes, capable of producing gain at the desired frequency, could be used.

Theory [edit]

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Colpitts oscillator model used in analysis at left.

One method of oscillator analysis is to determine the input impedance of an input port neglecting any reactive components. If the impedance yields a negative resistance term, oscillation is possible. This method will be used here to determine conditions of oscillation and the frequency of oscillation.

An ideal model is shown to the right. This configuration models the common collector circuit in the section above. For initial analysis, parasitic elements and device non-linearities will be ignored. These terms can be included later in a more rigorous analysis. Even with these approximations, acceptable comparison with experimental results is possible.

Ignoring the inductor, the input impedance can be written as

$Z_{in} = \frac{v_1}{i_1}$

Where $v_1$ is the input voltage and $i_1$ is the input current. The voltage $v_2$ is given by

$v_2 = i_2 Z_2$

Where $Z_2$ is the impedance of $C_2$ . The current flowing into $C_2$ is $i_2$ , which is the sum of two currents:

$i_2 = i_1 + i_s$

Where $i_s$ is the current supplied by the transistor. $i_s$ is a dependent current source given by

$i_s = g_m \left ( v_1 - v_2 \right )$

Where $g_m$ is the transconductance of the transistor. The input current $i_1$ is given by

$i_1 = \frac{v_1 - v_2}{Z_1}$

Where $Z_1$ is the impedance of $C_1$ . Solving for $v_2$ and substituting above yields

$Z_{in} = Z_1 + Z_2 + g_m Z_1 Z_2$

The input impedance appears as the two capacitors in series with an interesting term, $R_{in}$ which is proportional to the product of the two impedances:

$R_{in} = g_m \cdot Z_1 \cdot Z_2$

If $Z_1$ and $Z_2$ are complex and of the same sign, $R_{in}$ will be a negative resistance. If the impedances for $Z_1$ and $Z_2$ are substituted, $R_{in}$ is

$R_{in} = \frac{-g_m}{\omega ^ 2 C_1 C_2}$

If an inductor is connected to the input, the circuit will oscillate if the magnitude of the negative resistance is greater than the resistance of the inductor and any stray elements. The frequency of oscillation is as given in the previous section.

For the example oscillator above, the emitter current is roughly 1 mA. The transconductance is roughly 40 mS. Given all other values, the input resistance is roughly

$R_{in} = -30 \ \Omega$

This value should be sufficient to overcome any positive resistance in the circuit. By inspection, oscillation is more likely for larger values of transconductance and smaller values of capacitance. A more complicated analysis of the common-base oscillator reveals that a low frequency amplifier voltage gain must be at least four to achieve oscillation.^[6] The low frequency gain is given by:

$A_v = g_m \cdot R_p \ge 4$

If the two capacitors are replaced by inductors and magnetic coupling is ignored, the circuit becomes a Hartley oscillator. In that case, the input impedance is the sum of the two inductors and a negative resistance given by:

$R_{in} = -g_m \omega ^ 2 L_1 L_2$

In the Hartley circuit, oscillation is more likely for larger values of transconductance and larger values of inductance.

Oscillation amplitude [edit]

The amplitude of oscillation is generally difficult to predict, but it can often be accurately estimated using the describing function method.

For the common-base oscillator in Figure 1, this approach applied to a simplified model predicts an output (collector) voltage amplitude given by:^[7]

$V_C = 2 I_C R_L \frac{C_2}{C_1 + C_2}$

where $I_C$ is the bias current, and $R_L$ is the load resistance at the collector.

This assumes that the transistor does not saturate, the collector current flows in narrow pulses, and that the output voltage is sinusoidal (low distortion).

This approximate result also applies to oscillators employing different active device, such as MOSFETs and vacuum tubes.

External links [edit]

Java Simulation of a Colpitts oscillator

References [edit]

^ US 1624537, Colpitts, Edwin H., "Oscillation generator", published 1 February 1918, issued 12 April 1927
^ Gottlieb, Irving Gottlieb (1997). Practical Oscillator Handbook. US: Elsevier. p. 151. ISBN 0750631023.
^ Carr, Joe (2002). RF Components and Circuits. US: Newnes. p. 127. ISBN 0750648449.
^ Basak, A. (1991). Analogue Electronic Circuits and Systems. UK: Cambridge University Press. p. 153. ISBN 0521360463.
^ Rohde, Ulrich L.; Matthias Rudolph (2012). RF / Microwave Circuit Design for Wireless Applications, 2nd Ed.. John Wiley & Sons. pp. 745–746. ISBN 1118431405.
^ Razavi, B. Design of Analog CMOS Integrated Circuits. McGraw-Hill. 2001.
^ Trade-Offs in Analog Circuit Design: The Designer's Companion, Part 1 By Chris Toumazou, George S. Moschytz, Barrie Gilbert [1]

Lee, T. The Design of CMOS Radio-Frequency Integrated Circuits. Cambridge University Press. 2004.
Ulrich L. Rohde, Ajay K. Poddar, Georg Böck "The Design of Modern Microwave Oscillators for Wireless Applications ", John Wiley & Sons, New York, NY, May, 2005, ISBN 0-471-72342-8.
George Vendelin, Anthony M. Pavio, Ulrich L. Rohde " Microwave Circuit Design Using Linear and Nonlinear Techniques ", John Wiley & Sons, New York, NY, May, 2005, ISBN 0-471-41479-4.

v t e Electronic oscillators

Theory	Barkhausen stability criterion Harmonic oscillator Leeson's equation Nyquist stability criterion Oscillator phase noise Phase noise

LC oscillators	Armstrong oscillator Clapp oscillator Colpitts oscillator Hartley oscillator Vackář oscillator

RC oscillators	Phase-shift oscillator Twin-T oscillator Wien bridge oscillator

Quartz oscillators	Butler oscillator Pierce oscillator Tri-tet oscillator

Relaxation oscillators	Blocking oscillator Multivibrator

Other	Cavity oscillator Delay line oscillator Opto-electronic oscillator Robinson oscillator Transmission line oscillator

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